Abstract: Reducing the peak-to-average power ratio of a signal comprises receiving the input signal, where the input signal is associated with at least one unacceptable frequency range. The input signal is clipped about an amplitude range to yield a clipped signal and clipped information, where the clipped information represents intermodulation products. The clipped information is filtered to yield an error signal. The error signal represents a subset of the intermodulation products, where an intermodulation product of the subset corresponds to the unacceptable frequency range. The error signal is subtracted from the input signal to yield an output signal.

Abstract: A detector (20) is provided for use in a communication receiver where a received spread spectrum data signal is detected using a locally generated reference signal to decode the data signal. The detector (20) includes first (22) and second channels (24) and circuitry (90) for applying the received encoded data signal to the first (22) and second channels (24). A local generator (50) is provided for generating the reference signal wherein the reference signal has polarity transitions. A demodulator (40) is included in the first channel (22) for generating a detected recovered data signal from the received data signal in response to the reference signal. Circuitry (52) is provided for detecting the polarity transitions in the reference signal and for generating a differential PN signal. Circuitry (42) is further provided in the second channel (24) for correlating the received data signal and the differential PN signal to thereby generate a recovered error signal.

Abstract: A method and apparatus for baseband synchronizing of a local PN code sequence with a received PN code sequence incorporated in a received spread spectrum signal is provided. The received spread spectrum signal is translated to baseband to produce an I (in-phase) channel baseband signal and a Q (quadrature-phase) channel baseband signal. Data and error baseband correlators correlate the I channel and Q channel baseband signals with in-phase and quadrature-phase PN signals incorporating the local PN code sequence to produce despread on-time, advanced and delayed I channel and Q channel baseband signals. These despread baseband signals are processed and combined to produce an error signal proportional to a difference between the local PN code sequence and the received PN code sequence. A numerically-controlled oscillator circuit is responsive to the error signal to advance or delay the phase of a reference PN clock signal used to form a local PN clock signal.

Abstract: A method and apparatus for phase modulating a carrier signal to convey an information signal (12) such that the carrier signal has a constant amplitude envelope. A Hilbert transform signal (14) of the information signal (12) is produced. The signals (12, 14) are sampled to produce signals (16, 18), which represent cartesian coordinate values. The cartesian coordinate values are then converted into equivalent polar vectors (20-36) which have both an amplitude (R) and an angle (.theta.). The polar vector quantity (R, .theta.) is converted into two unity amplitude vectors (A, B). The unity amplitude vectors (A, B) are offset from the polar vector quantity by an angle the cosine of which is proportional to the amplitude of the polar vector (R). The carrier signal is sequentially phase modulated phase angles of the unity amplitude vectors (A, B) for each sample period of the information signal.

Abstract: A method and apparatus for phase modulating a carrier signal to convey an information signal (12) such that the carrier signal has a constant amplitude envelope. A Hilbert transform signal (14) of the information signal (12) is produced. The signals (12, 14) are sampled to produce signals (16, 18), which represent cartesian coordinate values. The cartesian coordinate values are then converted into equivalent polar vectors (20-36) which have both an amplitude (R) and an angle (.theta.). The polar vector quantity (R,.theta.) is converted into two unity amplitude vectors (A, B). The unity amplitude vectors (A, B) are offset from the polar vector quantity by an angle the cosine of which is proportional to the amplitude of the polar vector (R). The carrier signal is sequentially phase modulated by each of the angles of the unity amplitude vectors (A, B) for each sample period of the information signal.

Abstract: A segmented, transversal correlator for use in a spread spectrum communications system accurately synchronizes to an incoming spread signal by passively searching for a particular section of a known reference PN code sequence. To achieve correlator lengths of greater than one data bit long, the correlator may comprise a plurality of correlation subsections, each including a loading register for storing a different section of the overall reference PN code sequence. A section of the PN code sequence is transferred into a circulating register in each subsection through a parallel transfer. The dynamic, circulating PN code sequence is then correlated against statically stored analog samples of the incoming spread signal. When the dynamic PN reference code sequence is aligned with the corresponding PN sequence in the analog samples, a correlation signal is produced and magnitude detected to form a signal which is applied to a summation circuit.

Abstract: A transversal correlator is disclosed for demodulating a phase shift keyed (PSK) signal. The PSK signal is mixed with a local oscillator signal to produce quadrature I-channel and Q-channel signals. The I-channel and Q-channel signals are sampled at a periodic rate and the samples are propagated through a shift register for each channel. A preselected pseudo noise signal is stored in a local register which has an output tap for each stage. Each of the analog shift registers has a stage corresponding to one of the stages of the local register. Each of the I-channel and Q-channel samples is multiplied by the binary state in the corresponding stage of the local register. This multiplying operation produces a plurality of product signals. Product signals for alternate samples of the I-channel signal are summed with alternate but offset samples of the Q-channel signal to produce a first summation signal.

Abstract: A recovery loop includes an analog circuit that mixes a fixed frequency signal from a temperature controlled oscillator (20) with an IF input to produce product signals corresponding to the quadrature components of data signals with frequency offset. A digital complex multiplier (32) is responsive to the product signals and to the output of a number controlled oscillator (34) to produce a digital output corresponding to the data signals. The output of the number controlled oscillator (34) is controlled by a digital phase lock loop.

Abstract: Three sample and hold circuits (26, 30 and 34) sample a received pulse amplitude modulated signal at twice the data bit frequency or timing of the received signal. The clock to the sample and hold circuits is timed so that three consecutive samples, two mid-bit samples and a transition sample are held in the circuits (26, 30 and 34) once every two sample periods. The mid-bit samples are added together by an adder (32) and divided by two in a divider (38) to provide an average. The transition sample is subtracted from this average in a subtractor (36) to produce an error signal. The error signal is normalized in a multiplier (44) using the reciprocal of the difference in magnitude between the two mid-bit samples to produce a normalized signal. A clock signal is generated by a voltage controlled oscillator (52) in response to the normalized signal at twice the bit frequency or bit timing and in synchronism therewith.

Abstract: A direct current responsive mixing circuit (10) includes three mixers (14, 16 & 18), each having one D.C. port and two A.C. ports. The D.C. ports are responsive to D.C. and A.C. signals, while the A.C. ports are responsive only to A.C. signals. One mixer (14) has an A.C. port (24) receiving a pump signal and a D.C. port (28) receiving an I input signal. A second mixer (16) has an A.C. port (26) receiving the pump signal and a D.C. port (32) receiving a Q input signal. The remaining A.C. ports of the first two mixers (14 and 16) are connected to the two A.C. ports (36 and 38) of the third mixer (18). An output signal having a component corresponding to the product of the I and Q input signals is produced at the D.C. port (40) of the third mixer (18). In this construction, the mixing circuit 10 is responsive to A.C. and D.C. input signals and may produce a D.C. output signal component.

Abstract: A variable frequency oscillator is disclosed wherein the magnitude of a signed digital input determines the output frequency. The variable oscillator includes a digital integrator circuit for performing a modulo 2.pi. digital integration of the input signal. The integrator circuit is connected to a digital quadrature circuit which converts the integrated input signal from its polar form into two digital control signals in the rectangular domain having a quadrature phase relationship. The control signals are utilized in analog form by their combination with a high frequency carrier and its quadrature phase to synthesize the desired output frequency in an analog embodiment. According to another embodiment the quadrature synthesis is provided by the digital combination of the control signals and the phased carrier components.

Abstract: A nonlinearly variable gain circuit is utilized to produce an inverted logarithmic S curve of gain versus potentiometer rotation while using a linear resistance taper potentiometer. An operational amplifier feedback circuit uses the linear potentiometer and a resistance network in combination.