Constant-frequency control circuit for a switching voltage regulator of the hysteretic type

Abstract

The invention relates to a control circuit for a hysteretic switching voltage regulator, which comprises a logic circuit driving an output stage; a hysteresis comparator comparing the voltage value at the output of the regulator with a reference voltage; a current sensor for sensing, through a comparator, the current drain of a load connected to the output of the regulator. This control circuit further comprises a device for adjusting the hysteresis range of the hysteresis comparator, and a hysteresis frequency sensing and controlling logic portion connected to the output of the hysteresis comparator, the logic portion acting on the frequency adjusting device.

Description

TECHNICAL FIELD

[0001] This invention relates to a constant-frequency control circuit for a switching voltage regulator of the hysteretic type. In particular, the invention relates to a control circuit for controlling a switching regulator, which circuit comprises a logic circuit driving an output stage, and a hysteresis comparator comparing the output voltage value of the regulator with a reference voltage.

BACKGROUND OF THE INVENTION

[0002] As is well known in this specific field of application, voltage regulators of the switching type are commonly utilized in the power supply to microprocessors.

[0003] The current drain to a microprocessor incorporated in a portable computer (notebook), e.g., of the battery-operated variety, is bound to jump up from near zero to a maximum value when the microprocessor is switched from a standby condition to a normal condition of operation.

[0004] Due to the parasitic resistance of a filter capacitor, connected to the output of the voltage regulator wherethrough the microprocessor is powered, the output voltage Vo of the regulator shows a drop at the leading edge of said current. In view of this, the regulator is required to respond as quickly as possible in order to regain the voltage drop.

[0005] The output stage of a switching regulator comprises a complementary pair of MOS power transistors, e.g., a high-side transistor HS and a low-side transistor LS, which are connected in series with each other. Obtaining a fast response from the switching regulator upon a drop occurring in the output voltage means essentially that the MOS transistor HS must be turned on, and the MOS transistor LS turned off, as quickly as possible.

[0006] Control circuits have been proposed in the past wherein the MOS transistor HS is turned on synchronously with a clock signal to impose a predetermined switching frequency. However, circuits to this design are regarded too slow because of a time delay Ts occurring, between a load transient and the turning on of the MOS transistor HS, which can equal the switching period.

[0007] Another requirement of a switching regulator is that it should include arrangements to reduce pulse skipping when the load current is too small. In fact, battery life is affected by the power dissipated to the switching operation.

[0008] A prior solution described in U.S. Pat. No. 5,825,165 to Micro Linear Corp., for example, proposes that the output voltage Vo present on the filter capacitor be compared with a reference voltage Vref using a hysteresis comparator. A regulator equipped with such a comparator is termed “hysteretic”.

[0009] The comparator thresholds are Vref+−Vh/2.

[0010] Thus, the comparator output is utilized to drive the MOS power transistors of the regulator output stage.

[0011] The comparator switching is produced by ripple on the output voltage Vo originating from a voltage drop through the parasitic resistance of the output capacitor.

[0012] This prior solution has adequate speed of response, but the switching frequency is heavily dependent on such parameters as inductance, parasitic resistance (ESR) of the output capacitor, and input and output voltages. In addition, the switching frequency is not constant through a load transient.

SUMMARY OF THE INVENTION

[0013] According to principles of the invention, a constant-frequency control circuit for controlling a switching voltage regulator is provided. The present control circuit has structural and functional features appropriate to enable the regulator to respond promptly to any drops in the output voltage, as well as appropriate to maintain a low switching frequency while the load current is relatively small.

[0014] The circuit employs a regulator which includes a hysteresis comparator, and providing it with a closed-loop control circuit capable of holding the steady-state frequency at a predetermined reference value, irrespective of the parameters affecting the regulator operation.

[0015] The control circuit comprises a device for adjusting the hysteresis range of said hysteresis comparator. In one embodiment, it includes a hysteresis frequency sensing and controlling logic portion connected to the output of said hysteresis comparator, said logic portion being arranged to act on said hysteresis range adjusting device.

[0016] The features and advantages of the control circuit according to the invention will be apparent from the following description of an embodiment thereof, given by way of example and not of limitation with reference to the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

[0017] FIG. 1 shows schematically a control circuit according to the invention, as associated with a switching voltage regulator.

[0018] FIG. 2 shows schematically the circuit and regulator of FIG. 1 in further detail.

[0019] FIG. 3 is a schematic detail view of the control circuit shown in FIG. 1.

[0020] FIGS. 4A, 4B and 4C show graphs, respectively of the hysteresis range control voltage Vc, the load current IL, and the output voltage Vo, all plotted against the same time base, for the switching regulator of FIG. 1 when under a high-load condition.

[0021] FIGS. 5A, 5B and 5C show graphs, respectively of the hysteresis range control voltage Vc, the load current IL, and the output voltage Vo, all plotted against the same time base, for the switching regulator of FIG. 1 when under a low-load condition.

DETAILED DESCRIPTION OF THE INVENTION

[0022] With reference to the drawing views, a control circuit for use with a switching voltage regulator 2, according to this invention, is generally shown at 1 in schematic form. Various regulator circuit design components are shown in schematic form, including an inductor L, a capacitor C, a resistor R, a switch S, as well as a hysteresis response circuit composed of a comparator 7 and a combination circuit 17.

[0023] Regulators 2 may be associated with microprocessors installed in batterypowered portable computers (notebooks) to regulate sharp transitions in current drain when switching from a standby state to a turned-on state. Of course, the control circuit of this invention could be alternatively associated with a switching regulator connected to drive some other electronic device in power applications.

[0024] The circuit 1 and regulator 2 is integrated in the same semiconductor integrated circuit in one embodiment. In other embodiments, it may be separate, having some external components and some integrated components on one or more chips.

[0025] The regulator 2 is detailed in FIG. 2, where it is shown to comprise a logic circuit 3 and first and second drivers 4, 5 for respective MOS power transistors HS, LS of an output stage 6.

[0026] The logic circuit 3 has control outputs, each connected to a corresponding one of the drivers 4, 5.

[0027] These drivers 4, 5 are essentially amplification circuit portions whereby each control terminal of the power transistors HS, LS can be driven.

[0028] The first driver 4 is supplied a voltage Vdriver, and has its output connected directly to the gate terminal of the high-side transistor HS. For this reason, the driver 4 is also termed a high-side driver in the technical language.

[0029] The second driver 5 is supplied the voltage Vdriver, and has its output connected directly to the gate terminal of the low-side transistor LS. For this reason, the driver 5 is also termed a low-side driver in the technical language.

[0030] The MOS power transistors HS and LS are connected in series with each other between a first or supply voltage reference Vin and a second or ground voltage reference GND.

[0031] An interconnection node X is provided between these transistors HS, LS and is connected to the first driver 4.

[0032] A bootstrap capacitor is placed between the first supply voltage reference Vin and the node X.

[0033] A Schottky diode Z is placed, in parallel with the second transistor LS, between the node X and ground.

[0034] An inductor L and a sense resistor Rs are connected in series between the node X and an output terminal OUT of the regulator 2. The resistor Rs functions as a current sensor to sense the current IL absorbed by the external load of the regulator.

[0035] Derived from the terminal OUT is the output voltage value Vo, illustratively shown applied to a microprocessor CPU.

[0036] A filter capacitor having a parasitic resistance esr is provided between the output terminal OUT and the ground GND.

[0037] The regulator 2 further comprises a hysteresis comparator 7 having a first input connected to the output terminal OUT of the regulator, and having a second input arranged to receive a reference voltage Vref for comparison of the output voltage value Vo from the regulator 2.

[0038] The output of the hysteresis comparator 7 is applied to one input of the logic circuit 3.

[0039] The regulator 2 also comprises a pair of comparators 8, 9 arranged to report rising above an upper threshold which corresponds to a maximum current drain Imax of the load connected to the regulator output, and falling below a lower threshold which corresponds to a minimum current drain Io of said load.

[0040] In particular, the comparator 9 is a zero-crossing type serving a function to be explained.

[0041] The input signals to the comparators 8, 9 are derived from the ends A, B of the sense resistor Rs which is connected in the vicinity of the output terminal OUT.

[0042] More particularly, the nodes A, B are connected to either inputs of the comparators 8, 9, the output of each comparator 8, 9 being connected to a corresponding input of the logic circuit 3.

[0043] Advantageously in this invention, the control circuit 1 is designed to improve the performance of the regulator 2.

[0044] For this purpose, the circuit 1 includes a device 10 for adjusting the oscillation frequency of said hysteresis comparator. Preferably, the device 10 is a charge pump having plural control inputs.

[0045] In the illustrative embodiment herein, the charge pump 10 has at least three inputs 12, 13, 14 and a control output 15 which acts on the regulator 2, specifically on the hysteresis comparator 7 of the regulator 2.

[0046] The circuit 1 also includes a logic portion 11 for sensing and controlling the working frequency of the hysteresis comparator 7. The sensing/controlling logic portion 11 comprises a logic gate P1 and a set of memory elements.

[0047] The logic gate P1 is preferably a two-input AND gate, although the skilled person in the art will recognize that this logic gate could be arranged to perform a different logic operation.

[0048] A first input of the logic gate P1 receives the signal being output by the zero-crossing comparator 9 of the regulator 2 through an inverter 16.

[0049] The other input of the logic gate P1 receives the output signal from the hysteresis comparator 7 via a monostable element M3 characterized by having a delay period T3. Advantageously, the element M3 is a re-triggerable one.

[0050] The output of the logic gate P1 is connected to the input 14 of the charge pump 10. A control signal received on the input 14 is effective to depress the value of a current Ichp in the charge pump 10.

[0051] The output from the hysteresis comparator 7 is also applied to a setting input T of a bistable memory element 18 of the T type.

[0052] This element 18 has a first output Q connected to the input 12 of the charge pump 10 through a monostable element M1 characterized by having a delay period Ts. In a preferred embodiment, T3 is greater than Ts.

[0053] A second output {overscore (Q)}, being the inverted signal of the first output Q, of the element 18 is connected to the other input 13 of the charge pump 10 through a further monostable element M2 characterized by also having a delay period Ts.

[0054] A control signal received on the input 12 or 13 is effective to integrate the current Ichp in the charge pump 10.

[0055] Shown schematically in FIG. 3 is the internal construction of the charge pump 10, whence it can be evinced that each input 12, 13 or 14 is essentially a normally open controlled switch 12′, 13′ or 14′ adapted to communicate a respective current generator to a center node N of the pump 10.

[0056] More particularly, a first current generator I1 is connected in series with the switch 12′ between ground GND and the node N.

[0057] A second current generator 12 is connected in series with the switch 13′ between ground GND and the node N; and a third current generator 13 is connected in series with the switch 14′ between ground GND and the node N. The generators I1 and I2 will pump a current to the node N, whereas the generator I3 will drain a current from the node N.

[0058] A charge capacitor C is connected in parallel with the last-mentioned series connection between the generator I3 and the switch 14′.

[0059] The output of the charge pump 10 is derived from the node N in the form of a control voltage Vc.

[0060] The operation of the control circuit 1 according to the invention will now be described.

[0061] Each time that the transistor HS in the output stage 6 is turned on, a pulse having a duration Ts (corresponding to a desired period of oscillation) is generated by means of the two monostable elements M1 and M2. These elements are controlled by the flip-flop FFI, each every two turn-on cycles of the transistor HS.

[0062] The pulses output by each monostable element M1, M2 are integrated by the charge pump 10 producing a current Ichp. Each time that the transistor HS of the regulator 2 is turned on, the monostable element M3 is controlled, whose pulse has a duration T3 slightly longer than the duration of Ts.

[0063] This pulse T3 is, in turn, integrated by means of a current -Ichp. The output from the charge pump 10 produces a voltage value Vc which is applied to the hysteresis comparator 7 of the regulator to control the width Vh of the hysteresis range of the comparator 7.

[0064] In the steady-state condition, the charge balance causes the system to oscillate at a frequency fs=1/Ts. The pulses output by the elements M1 and M2 are aligned (specifically, the output from M2 goes high at the trailing edge of M1, and vice versa), whereas the output from the element M3 is always high. With a control of this type, the control voltage Vc shows no ripple at steady-state. FIGS. 4A, 4B and 4C are graphs of the input voltage Vc, the load current IL, and the output voltage Vo, plotted against the same time base.

[0065] Upon the occurrence of a load transient, the transistor HS (or LS) stays ‘on’ for the time needed to bring the output voltage Vo of the regulator back within the hysteresis range. This time interval may be longer than the period Ts, so that the control voltage Vc will come down from the steady-state value and, consequently, the hysteresis range becomes narrower.

[0066] However, the output pulse from the element M3 will exhaust itself if this interval exceeds T3, thereby preventing the charge pump 10 from becoming too deeply discharged.

[0067] This control being of the first order, its stability can be quite robust.

[0068] The closed-loop frequency of the control may be chosen approximately one order of magnitude less than the frequency fs.

[0069] To set the switching frequency, it is necessary to set the duration of the pulse from the monostables M1, M2 and M3, such as by altering a reference current from outside the integrated circuit which contains the regulator 2.

[0070] The control circuit of this invention allows a situation of the load being very low to be handled with ease. In this case, the current in the inductor IL is zero and tends to turn negative during the half-cycle when the transistor HS is ‘off’ and the transistor LS is ‘on’.

[0071] The zero-crossing comparator 9 senses this circumstance, and turns off the transistor LS as required by the specifications for pulse skipping attenuation.

[0072] Both LS and HS stay ‘off’ (at current IL=0) until the output voltage Vo falls below the lower threshold (Vref−Vh/2) of the comparator 7, thus causing the transistor HS to be turned on.

[0073] During this time interval, the logic gate P1 will inhibit the charge pump 10 from being discharged. For charge balance, the time interval when the current IL is above zero (with HS or LS ‘on’) should equal Ts.

[0074] The control voltage Vc to the charge pump 10 has the same value as during normal operation, whereas the time interval when IL=0 depends on the load current.

[0075] The solution proposed by the invention might reveal some frequency instability during the load transients. In fact, frequency will rise above its steady-state value as soon as the output voltage Vo is brought back within the hysteresis range; subsequently to this, frequency will come down and then climb back to its steady-state value. This behavior will not be experienced during normal circuit operation and can only occur when duty cycle is very low (or when it approaches one).

[0076] This control circuit thus generally performs to solve the technical problems of the prior circuits and allows the width of the oscillation band of the hysteresis comparator incorporated in the switching regulator to be adjusted in an adaptative fashion.

[0077] This is effectively achieved by a circuit design which is most simple to implement and requires but a small circuit area.

[0078] From the foregoing it will be appreciated that, although specific embodiments of the invention have been described herein for purposes of illustration, various modifications may be made without deviating from the spirit and scope of the invention. Accordingly, the invention is not limited except as by the appended claims.

Claims

1. A control circuit for a hysteretic switching voltage regulator, comprising:

a logic circuit driving an output stage;

a hysteresis comparator comparing the voltage value at the output of the regulator with a reference voltage;

a current sensor for sensing, through a comparator, the current drain of a load connected to the output of the regulator;

a device for adjusting the hysteresis range of said hysteresis comparator; and

a hysteresis frequency sensing and controlling logic portion connected to the output of said hysteresis comparator, said logic portion being arranged to act on said frequency adjusting device.

2. The control circuit according to

claim 1 wherein said frequency adjusting device is a charge pump having plural control inputs.

3. The control circuit according to

claim 1 wherein said sensing/controlling logic portion comprises a logic gate being input the output signal from said hysteresis comparator and an output signal from said comparator to sense the load current drain.

4. The control circuit according to

claim 3 wherein the output from said logic gate is applied directly to an input of said frequency adjusting device.

5. The control circuit according to

claim 1 wherein said sensing/controlling logic portion comprises a memory element being input the output signal from said hysteresis comparator and having a pair of conjugated outputs connected to respective control inputs of said frequency adjusting device.

6. The control circuit according to

claim 5 wherein monostable elements, each having a delay period Ts, are connected between said matched outputs and respective inputs of the frequency adjusting device.

7. The control circuit according to

claim 3 wherein the output signal from said hysteresis comparator is applied to an input of said logic gate through a monostable element having a delay period T3.

8. The control circuit according to

claim 6 wherein the delay period T3 is longer than the delay period Ts.

9. The control circuit according to

claim 2 wherein said charge pump is constructed with a number of normally open controlled switches, each corresponding to one of said inputs, operative to communicate a respective one of current generators to the charge pump at a center circuit node N thereof.

10. The control circuit according to

claim 2 wherein a control voltage output from said charge pump is applied to said hysteresis comparator.