Abstract: A driver circuit 11 includes a plurality of cascode-connected NMOS transistors, a modulating signal VGN1 is applied to a gate terminal of a lowermost stage transistor TN1 located at a lowermost stage out of the NMOS transistors, and an upper stage bias potential VGN2 that is a sum of a minimum gate-source voltage VGN1min and a maximum drain-source voltage VDS1max of a transistor (TN1) located immediately below an upper stage transistor located at an upper stage above the lowermost stage transistor of the NMOS transistors is applied to the upper stage transistor TN2.

Abstract: An optical modulator driver circuit (1) includes an amplifier (50, Q10, Q11, R10-R13), and a current amount adjustment circuit (51) capable of adjusting a current amount of the amplifier (50) in accordance with a desired operation mode. The current amount adjustment circuit (51) includes at least two current sources (IS10) that are individually ON/OFF-controllable in accordance with a binary control signal representing the desired operation mode.

Abstract: A positive-side power supply terminal (1-1a) of a differential amplifier (1-1) is connected to a positive-side power supply line (L1). A negative-side power supply terminal (1-2b) of a differential amplifier (1-2) is connected to a negative-side power supply line (L2). A negative-side power supply terminal (1-1b) of the differential amplifier (1-1) and a positive-side power supply terminal (1-2a) of the differential amplifier (1-2) are connected to each other. A final-stage amplifier (2) is connected between the positive-side power supply line (L1) and the negative-side power supply line (L2).

Abstract: A connection structure (3) of a high-frequency transmission line according to this invention includes a columnar central conductor (7) having one end connected to a coaxial line and the other end connected to a planar transmission line, a first outer conductor (41) arranged on a side of the one end of the central conductor coaxially with the central conductor, a first dielectric body (42) filled between the first outer conductor and the central conductor, a second outer conductor (61) arranged on a side of the other end of the central conductor coaxially with the central conductor, a second dielectric body (62) filled between the second outer conductor and the central conductor, a third outer conductor (51) arranged between the first outer conductor and the second outer conductor coaxially with the central conductor, and a third dielectric body (52) filled between the third outer conductor and the central conductor.

Abstract: In the conventional technique, only an output having a bandwidth identical to the bandwidth of individual DACs has been obtained even by using a plurality of DACs. Also, even when the output of a bandwidth broader than the individual DAC is obtained, there has been a problem associated with asymmetricity of a circuit configuration. In a signal generating device of the present invention, a plurality of normal DACs are combined to realize an analog output of a broader bandwidth beyond the output bandwidth of the individual DACs, and the problem of the asymmetricity of the circuit configuration is also resolved. A desired signal is separated into a low-frequency signal and a high-frequency signal in a frequency domain, and a series of operation of constant (r)-folding the amplitude of the high-frequency signal and shifting it on the frequency axis to superimpose it on the low-frequency signal are made in a digital domain. The output of each DAC is switched by an analog multiplexer.

Abstract: In the conventional technique, only an output having a bandwidth identical to the bandwidth of individual DACs has been obtained even by using a plurality of DACs. Also, even when the output of a bandwidth broader than the individual DAC is obtained, there has been a problem associated with asymmetricity of a circuit configuration. In a signal generating device of the present invention, a plurality of normal DACs are combined to realize an analog output of a broader bandwidth beyond the output bandwidth of the individual DACs, and the problem of the asymmetricity of the circuit configuration is also resolved. A desired signal is separated into a low-frequency signal and a high-frequency signal in a frequency domain, and a series of operation of constant (r)-folding the amplitude of the high-frequency signal and shifting it on the frequency axis to superimpose it on the low-frequency signal are made in a digital domain. The output of each DAC is switched by an analog multiplexer.

Abstract: An analog multiplexer core circuit (120A) includes a differential pair (121) that includes two transistors (Q1, Q2), a differential pair (122) that includes two transistors (Q3, Q4), a differential pair (123) that includes two transistors (Q5, Q6), and a constant current source (124) that causes a current (IEE) to flow. This analog multiplexer core circuit (120A) time-multiplexes two analog signals (Ain1, Ain2) and outputs a time-multiplexed analog signal (Aout). Each emitter resistor (REA1, REA2, REA3, REA4) is connected to a corresponding one of the transistors (Q1, Q2, Q3, Q4). At this time, a relation of “REA·IEE?the amplitude of an input analog signal” is satisfied. As a result, linearity of response can be ensured by expanding the linear response input range of the differential pairs (121, 122).

Abstract: In the conventional technique, only an output having a bandwidth identical to the bandwidth of individual DACs has been obtained even by using a plurality of DACs. Also, even when the output of a bandwidth broader than the individual DAC is obtained, there has been a problem associated with asymmetricity of a circuit configuration. In a signal generating device of the present invention, a plurality of normal DACs are combined to realize an analog output of a broader bandwidth beyond the output bandwidth of the individual DACs, and the problem of the asymmetricity of the circuit configuration is also resolved. A desired signal is separated into a low-frequency signal and a high-frequency signal in a frequency domain, and a series of operation of constant (r)-folding the amplitude of the high-frequency signal and shifting it on the frequency axis to superimpose it on the low-frequency signal are made in a digital domain. The output of each DAC is switched by an analog multiplexer.

Abstract: An optical modulator driver circuit (1) includes an amplifier (50, Q10, Q11, R10-R13), and a current amount adjustment circuit (51) capable of adjusting a current amount of the amplifier (50) in accordance with a desired operation mode. The current amount adjustment circuit (51) includes at least two current sources (IS10) that are individually ON/OFF-controllable in accordance with a binary control signal representing the desired operation mode.

Abstract: A frequency domain multiplexed signal receiving method which decodes received signals that are multiplexed in a frequency domain, includes: a digital signal acquisition step of acquiring digital signals from the received signals that are multiplexed in the frequency domain; an offset discrete Fourier transform step of applying an offset discrete Fourier transform to odd discrete point numbers based on the acquired digital signals; and a decode step of decoding frequency domain digital signals in the frequency domain obtained by the offset discrete Fourier transform, and that are the frequency domain digital signals of one or more frequency channels.

Abstract: An automatic gain control circuit (5a) includes a peak detector circuit (10) that detects the peak voltage of the output signal from a variable gain amplifier (3), an average value detection and output amplitude setting circuit (11) that detects the average voltage of the output signals from the variable gain amplifier (3) and adds a voltage ½ the desired output amplitude of the variable gain amplifier (3) to the average voltage, and a high gain amplifier (12) that amplifies the difference between the output voltage of the peak detector circuit (10) and the output voltage of the average value detection and output amplitude setting circuit (11) and controls the gain of the variable gain amplifier (3) using the amplification result as a gain control signal. The peak detector circuit (10) includes transistors (Q1, Q2, Q3), a current source (I1), and a filter circuit. The filter circuit includes a series connection of a resistor (Ra) and a capacitor (C1).

Abstract: An automatic gain control circuit (5a) includes a peak detector circuit (10) that detects the peak voltage of the output signal from a variable gain amplifier (3), an average value detection and output amplitude setting circuit (11) that detects the average voltage of the output signals from the variable gain amplifier (3) and adds a voltage ½ the desired output amplitude of the variable gain amplifier (3) to the average voltage, and a high gain amplifier (12) that amplifies the difference between the output voltage of the peak detector circuit (10) and the output voltage of the average value detection and output amplitude setting circuit (11) and controls the gain of the variable gain amplifier (3) using the amplification result as a gain control signal. The peak detector circuit (10) includes transistors (Q1, Q2, Q3), a current source (I1), and a filter circuit. The filter circuit includes a series connection of a resistor (Ra) and a capacitor (C1).

Abstract: A voltage generator (400) includes a resistor ladder including resistors (4000-4008) which divide a supplied voltage to generate a plurality of reference voltages, a resistor (4009) provided between a power supply voltage (VCC) and one terminal of the resistor ladder, and a resistor (4010) provided between a power supply voltage (VEE) and the other terminal of the resistor ladder.

Abstract: A vector sum phase shifter includes a 90° phase shifter (1) which generates an in-phase signal (VINI) and a quadrature signal (VINQ) from an input signal (VIN), a four-quadrant multiplier (2I) which changes the amplitude of the in-phase signal (VINI) based on a control signal (CI), a four-quadrant multiplier (2Q) which changes the amplitude of the quadrature signal (VINQ) based on a control signal (CQ), a combiner (3) which combines the in-phase signal (VINI) and the quadrature signal (VINQ), and a control circuit (4). The control circuit (4) includes a voltage generator which generates a reference voltage, and a differential amplifier which outputs the difference signal between a control voltage (VC) and the reference voltage as the control signal (CI, CQ). The differential amplifier performs an analog operation of converting the control voltage (VC) into the control signal (CI, CQ) similar to a sine wave or a cosine wave.

Abstract: In a signal output circuit, an input buffer externally receives a single-phase switching instruction signal to switch a state of the output circuit a shutdown disable state or a shutdown enable state, and converts and outputs the single-phase switching instruction signal into a differential switching instruction signal. A generation control circuit outputs a generation control signal for controlling generation of a control voltage in the control voltage generation circuit based on the differential switching instruction signal. A control voltage generation circuit outputs the control voltage upon changing a value of the control voltage in accordance with a logic of the single-phase switching instruction signal. An output circuit externally receives a differential input signal, outputs a differential output signal upon impedance-converting the differential input signal, and switches between the shutdown disable state and the shutdown enable state of the differential input signal.

Abstract: In an automatic gain control circuit, a peak detection circuit detects and outputs the peak voltage of an output signal from a variable gain circuit. An average value detection/output amplitude setting circuit detects the average value voltage of an output signal from the variable gain circuit, and outputs a calculated voltage. An amplification circuit controls the gain of the variable gain circuit by amplifying the difference between the output voltages of the peak detection circuit and average value detection/output amplitude setting circuit. The number of base-emitter junctions of transistors on a path in the peak detection circuit from input ports which receive output signals from the variable gain circuit to an output port which outputs a voltage to the amplification circuit is equal to the number of base-emitter junctions of transistors on a path in the average value detection/output amplitude setting circuit.

Abstract: Two D flip-flops (D-FFMA, D-FFMB) output two half-rate signals (DMR-A, DMR-B) by dividing a digital input signal (DM) into two signals and retiming them based on a clock signal (CLK) and a negative-phase clock signal (CLKB). First and second switches (SM1, SM2) are driven by the two half-rate signals (DMR-A, DMR-B). Third and fourth switches (SM3, SM4) are driven by a select signal SW and a negative-phase select signal SWB that have the same frequency as that of the clock signal (CLK) but a different phase from that of the clock signal (CLK). The current supplied from a current source (1) to a load (4) thus becomes a current signal corresponding to a conversion frequency twice the frequency of the clock signal (CLK).

Abstract: A receiver device receives a signal inputted to one or a plurality of ports as a plurality of received signals, and includes: a phase offset estimating unit that, on the basis of a unique word of each signal block contained in said received signal, estimates the phase offset, and a phase offset compensating unit that, on the basis of a phase offset estimated by said phase offset estimating unit, compensates the phase offset; the receiver device uses a known signal component (unique word) contained in a frequency-domain equalized signal to compensate the phase offset, whereby it compensates complex phase offset fluctuation, and estimates the phase offset of a signal obtained at each port.

Abstract: In an automatic gain control circuit, a peak detection circuit detects and outputs the peak voltage of an output signal from a variable gain circuit. An average value detection/output amplitude setting circuit detects the average value voltage of an output signal from the variable gain circuit, and outputs a calculated voltage. An amplification circuit controls the gain of the variable gain circuit by amplifying the difference between the output voltages of the peak detection circuit and average value detection/output amplitude setting circuit. The number of base-emitter junctions of transistors on a path in the peak detection circuit from input ports which receive output signals from the variable gain circuit to an output port which outputs a voltage to the amplification circuit is equal to the number of base-emitter junctions of transistors on a path in the average value detection/output amplitude setting circuit.

Abstract: In a signal output circuit, an input buffer externally receives a single-phase switching instruction signal to switch a state of the output circuit a shutdown disable state or a shutdown enable state, and converts and outputs the single-phase switching instruction signal into a differential switching instruction signal. A generation control circuit outputs a generation control signal for controlling generation of a control voltage in the control voltage generation circuit based on the differential switching instruction signal. A control voltage generation circuit outputs the control voltage upon changing a value of the control voltage in accordance with a logic of the single-phase switching instruction signal. An output circuit externally receives a differential input signal, outputs a differential output signal upon impedance-converting the differential input signal, and switches between the shutdown disable state and the shutdown enable state of the differential input signal.